Calibration protocol for command and address bus voltage reference in low-swing single-ended signaling

ABSTRACT

A single-ended receiver is coupled to an input-output (I/O) pin of a command and address (CA) bus. The receiver is configurable with dual-mode I/O support to operate the CA bus in a low-swing mode and a high-swing mode. The receiver is configurable to receive a first command on the I/O pin while in the high-swing mode, initiate calibration of the slave device to operate in the low-swing mode in response to the first command, switch the slave device to operate in the low-swing mode while the CA bus remains active, and to receive a second command on the I/O pin while in the low-swing mode.

RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.16/145,837, filed Sep. 28, 2018, which is a continuation of U.S. patentapplication Ser. No. 15/616,785, now U.S. Pat. No. 10,089,256, filedJun. 7, 2017, which is a continuation of U.S. patent application Ser.No. 14/080,724, filed on Nov. 14, 2013, now U. S. Pat. No. 9,715,467,which claims the benefit of U.S. Provisional Application No. 61/730,018,filed Nov. 26, 2012, the entire contents of all are incorporated byreference.

BACKGROUND

Computing memory systems are generally composed of one or more dynamicrandom access memory (DRAM) integrated circuits, referred to herein asDRAM devices, which are connected to one or more processors. MultipleDRAM devices may be arranged on a memory module, such as a dual in-linememory module (DIMM). A DIMM includes a series of DRAM devices mountedon a printed circuit board (PCB) and are typically designed for use inpersonal computers, workstations, servers, or the like. There aredifferent types of memory modules, including a load-reduced DIMM(LRDIMM) for Double Data Rate Type three (DDR3), which have been usedfor large-capacity servers and high-performance computing platforms.Memory capacity may be limited by the loading of the data query (DQ) busand the request query (RQ) bus associated with the user of many DRAMdevices and DIMMs. LRDIMMs may increase memory capacity by using amemory buffer (also referred to as a register). Registered memorymodules have a register between the DRAM devices and the system's memorycontroller. For example, a fully buffered DIMM architecture introducesan advanced memory buffer (AMB) between the memory controller and theDRAM devices on the DIMM. The memory controller communicates with theAMB as if the AMB were a memory device, and the AMB communicates withthe DRAM devices as if the AMB were a memory controller. The AMB canbuffer data, command and address signals. With this architecture, thememory controller does not write to the DRAM devices, rather the AMBwrites to the DRAM devices. This architecture introduces latency to thememory request and increases power consumption for the AMB.

BRIEF DESCRIPTION OF THE DRAWINGS

The present embodiments are illustrated by way of example, and not oflimitation, in the figures of the accompanying drawings in which:

FIG. 1 is a block diagram illustrating receiver architecture withdual-mode swing support according to one embodiment.

FIG. 2 is a block diagram illustrating the receiver architecture of FIG.1 during a transition from a high-swing mode to a low-swing modeaccording to one embodiment.

FIG. 3 is a block diagram illustrating the receiver architecture of FIG.1 during the transition from a high-swing mode to a low-swing modeaccording to one embodiment.

FIG. 4 is a high-level block diagram illustrating a single-endedcommunication system that uses a transmitter and a receiver withdual-mode swing support according to another embodiment.

FIG. 5 is a high-level block diagram illustrating a single-ended memorysystem including a memory controller and a DRAM device with dual-modeswing support according to another embodiment.

FIG. 6 is a flow diagram of a method of operating a device including areceiver with dual-mode swing support according to an embodiment.

FIG. 7 is a flow diagram of a method of operating a DRAM and a memorycontroller according to another embodiment.

FIG. 8 is a flow diagram of the method of operating a DRAM and a memorycontroller according to another embodiment.

FIG. 9 is a diagram of a voltage generation circuit including a constantresistance with a variable current.

FIG. 10 is a diagram of a voltage generation circuit including aconstant current and a variable resistance.

FIG. 11 is a diagram of a voltage generation circuit including aresistor divider and a variable resistance.

FIG. 12 is a diagram of a computer system, including main memory withdual-mode swing support according to one embodiment.

FIG. 13 is a timing diagram of the receiver architecture with dual-modeswing support in a high-swing mode before transition to a low-swing modeaccording to one embodiment.

FIG. 14 is a timing diagram of the receiver architecture with dual-modeswing support in a low-swing mode after transition from a high-swingmode according to one embodiment.

FIGS. 15-18 illustrate four steps of the transition from a high-swingmode to a low-swing mode according to one embodiment.

DETAILED DESCRIPTION

In typical DRAM devices, a command and address (CA) bus is usually in ahigh-swing mode to ensure that the CA bus is fully functional at boot-upwithout the need for calibration of a reference voltage (Vref). However,low-swing signaling on the CA bus would allow lower active power andre-use of design blocks, including transmitters and receivers, for boththe CA bus and the data (also referred to herein as the data request(DQ) bus) if the data bus uses low-swing signaling. Typically, inlow-swing, single-ended signaling, Vref calibration on the CA bus needsto be completed before commands can be issued reliably to a single-endedreceiver, such as a receiver of a memory device (e.g., DRAM device). TheVref calibration command needs to be sent on the CA bus when there is nosideband register interface to the memory device. As a result, someconventional designs use high-swing receivers for both CA and DQ andothers uses high-swing receivers for CA while DQ is low swing as theycan be calibrated using commands decoded through the CA bus. Theembodiments described herein provide dual-mode swing receivers thatallow the receivers to operate in two modes, a high-swing mode and alow-swing mode. These dual-mode swing receivers can be used for the CAbus, and thus, the memory controller and the memory devices can beconfigured for dual-mode swing support.

The embodiments describe a method and protocol for calibrating thereference voltage of the CA bus so that it can operate with low swingduring operational mode. The commands are initially sent using ahigh-swing mode, which is decoded to do internal calibration, which getsthe receivers to operate in a low-swing mode. In one embodiment, thememory controller and the memory device boot up in high-swing, low-datarate mode for the transmitter and receiver in the command and data bus.The proposed embodiments can work for high-swing high-data rate duringstartup as well, which can be used to reduce or eliminate low speedstartup. The memory device can receive a command in the high-swing modeto prepare for transitioning the memory device to low-swing mode. Thiscommand can be referred to as a low-swing transition command.Alternatively, the memory controller can enable internal Vref in theDRAM device and program the DRAM device to low-swing mode on DQ and CA.The memory does the preparation for calibration to the low-swing mode inhigh-swing mode and programs the DRAM to the low-swing mode. The memorycontroller switches to low-swing (e.g., high frequency mode), andtoggles a single command signal to initiate actual CA Vref calibrationon the memory device with low-swing input-output (I/O). This commandsignal may be considered a Vref calibration command. The CA iscalibrated by the memory device for low-swing operation. An additionalVref calibration step may be needed for the toggled command signal.

FIG. 1 is a block diagram illustrating receiver architecture 100 withdual-mode support according to one embodiment. The receiver architecture100 has one or more CA address and command pins 180 and a common node115. The common node 115 includes a voltage divider and a switch toenable and disable the voltage divider. The voltage divider is togenerate a default voltage reference 113 (referred to herein as defaultVref). For example, the default Vref can be 200 mV for the defaulthigh-swing mode. The common node 115 also includes a pin 118 thatprovides an external Vref 151 (referred to as Vref CA). Each of the oneor more CA address and command pins 180 includes a voltage generationcircuit 110, a reference voltage calibration controller (Vrefcalibration controller) 150, a preamp 120, a filter 116, a firstmultiplexer 112, a second multiplexer 114, a common mode logic to CMOSlogic (CML2CMOS) circuit 122, a receiver front end 117 (Rx Front End).The receiver architecture 100 receives data on a pin 108. The data couldbe command signals, address signals, or other control signals for the CAbus. The Vref calibration controller 150 is used to calibrate theinternal Vref 154, but may also be used to coordinate the transitionbetween the high-swing and low-swing modes. In one implementation, theVref calibration controller 150, which is used in connection with thevoltage generation circuit 110, has logic that sets the internal Vref154 generated by the voltage generation circuit 110. In one embodiment,the voltage generation circuit 110 comprises an internal Vref DAC(herein after referred to as internal DAC) to generate an internal Vref154. In particular, the Vref calibration controller 150 may includelogic that provides an offset to the internal DAC (or other type ofvoltage generation circuit), and the internal DAC generates the internalVref 154 based on the offset. Alternatively, other types of voltagegeneration circuits than an internal DAC may be used as would beappreciated by one of ordinary skill in the art having the benefit ofthis disclosure. The first multiplexer 112 receives the incoming signalon the pin 108 (e.g., CAo-CAN, where N represents the number of pins ofthe CA bus). The output of the first multiplexer 112 is coupled to afirst terminal of the receiver front end 117 (RxP). Using a clockpattern or any of the direct current balanced patterns at the input, anaverage can be calculated to get the common mode 111 using one of thefollowing options: 1) passive filters (e.g., RC filter); 2) switchedcapacitor filter; and 3) low bandwidth amplifier (e.g., voltagefollower). The first multiplexer 112 can be used to switch in the filter116 during steps of the dual-mode calibration process described belowwith respect to FIGS. 2-3. Alternatively, the first multiplexer 112 canbe other types of selection circuits as would be appreciated by one ofordinary skill in the art having the benefit of this disclosure.

The preamp 120 receives the internal Vref 154 and the external Vref 151on the pin 118. In particular, the preamp 120 can receive the internalVref 154 during some steps of the calibration process and the externalVref 151 during different steps of the dual-mode calibration processdescribed below with respect to FIGS. 2-3. The output of the preamp 120is coupled to the CML2CMOS circuit 122 and the output of the CML2CMOScircuit 122 can be feedback to the logic 151 of the Vref calibrationcontroller 150. The Vref calibration circuit 150 can control the voltagegeneration circuit 110 to set or calibrate the internal Vref 154. FIGS.9-11 illustrate different embodiments of the voltage generation circuit110.

FIG. 9 is a diagram of a voltage generation circuit 900 including aconstant resistance with a variable current. The voltage generationcircuit 900 includes six current sources (transistors) that arecontrolled by six switches, which are activated by trim signals (e.g.,Trim<5:0>) received from the logic of the Vref calibration controller150, and a resistor coupled to common ground. In other implementations,other number of current source transistors could be used. This voltagegeneration circuit 110 could be considered a constant resistor withvariable current (as indicated by the arrow across the transistors).Also, in other implementations, other types of voltage generationcircuits may be used as would be appreciated by one of ordinary skill inthe art having the benefit of this disclosure. The voltage generationcircuit 110 may be a circuit with constant current with variableresistance, a circuit with constant resistance with variable current, acircuit with a resistor divider with one being variable resistor, acircuit with active devices instead of resistors in any of the resistorcombinations, or switched capacitance based adjustable voltage divider.In another embodiment, as illustrated in FIG. 10, a voltage generationcircuit 1000 includes a constant current, as controlled by the trimsignals from the Vref calibration controller, and a variable resistance(as indicated by the arrow across multiple resistors). In anotherembodiment, as illustrated in FIG. 11, a voltage generation circuit 1100includes a resistor divider, as controlled by the trim signals from theVref calibration controller, and a variable resistance (as indicated bythe arrow across multiple resistors). Furthermore, there are othervariations for these voltage generation circuits 110, 900, 1000, and1100, including switching the top and bottom portions of the circuit,using PMOS or NMOS transistors, using active devices instead of passiveresistors, or using any other voltage divider types as would beappreciated by one of ordinary skill in the art having the benefit ofthis disclosure.

A second multiplexer 114 is coupled to receive the default Vref 113, asdescribed above, and the internal Vref 154. The output of the secondmultiplexer 114 is coupled to a second terminal of the receiver frontend 117 (RxN). The second multiplexer 114 can be used to switch betweenthese two reference voltages during steps of the dual-mode calibrationprocess described below with respect to FIGS. 2-3. Alternatively, thesecond multiplexer 114 can be other types of selection circuits as wouldbe appreciated by one of ordinary skill in the art having the benefit ofthis disclosure.

As described above, in typical DRAM devices, the CA bus is usually in ahigh-swing mode to ensure that the CA bus is fully functional at boot-upwithout the need for Vref calibration. The embodiments described hereinprovide low-swing signaling on the CA bus to allow lower active powerand to re-use design for the DQ and CA receivers and transmitters. Theembodiments described herein provide dual-mode swing receivers thatallow the receivers to operate in two modes, a high-swing mode and alow-swing mode. These dual-mode swing receivers can be used for the CAbus, and thus, the memory controller and the memory devices can beconfigured for dual-mode swing support. The dual-mode swing support ison transmission levels at the CPHY (controller side) and MPHY (memoryside). For example, the low-swing near ground signaling (NGS) is 250 mVswing at full speed, such as 1.6 Gbps single data rate (SDR) andhigh-swing NGS is 400 mV at boot frequency (slower than full speed). NGSis a single-ended, ground-terminated signaling technology that enableshigh data rates at significantly reduced input output (IO) signalingpower and design complexity, while maintaining excellent signalintegrity. For example, NGS enables high performance single-endedsignaling by lowering the operating voltage to 0.5V and maintainingrobust signal integrity at near ground levels. NGS may also decreaseactive IO power consumption by lowering the signal swing and terminatingto ground. The lower IO voltage may be better matched to the operatingvoltage of advanced CPU's and GPU's and reduce the cost and complexityof integrating the memory controller on the processor chip.

The embodiments describe a method and protocol for calibrating thereference voltage of the CA bus so that it can operate with low swingduring operational mode. As described above, the commands are initiallysent using a high-swing mode, which is decoded to do internalcalibration, which gets the receivers to operate in a low-swing mode, asdescribed in more detail with respect to FIGS. 2-3.

FIG. 2 is a block diagram illustrating the receiver architecture 100 ofFIG. 1 during a transition from a high-swing mode to a low-swing modeaccording to one embodiment. The single-ended transmitter and receiverof the CA bus boot up in a high-swing mode. In particular, the secondmultiplexer 114 receives a default Vref 113 from the common node 115 ina step 202 (step 1). In the depicted embodiment, an internal resistordivider from Vdd generates the default Vref 113 to be used in thehigh-swing mode. In one implementation, the default Vref 113 is 200 mVreference. Of course, other reference voltages may be used for thehigh-swing mode based on the design of the receiver architecture 100.

While in the high-swing mode, the first multiplexer 112 receive a firstcommand (e.g., a low-swing transition command) to transition thereceiver to a low-swing mode on the pin 108 in step 204 (step 1). Thefirst low-swing transition command is received from the single-endedtransmitter on the pin 108. The receiver decodes the first command,which calibrates per pin, including determining an offset for thevoltage generation circuit 110, which generates the internal Vref 154and determining the low-swing Vref at step 206 (step 2). Oneimplementation combines both offset and low-swing Vref calibration in asingle step, step 2. Alternatively, these could be separate steps. Instep 2, the preamp 120 receives the external Vref 151 on the pin 118, aswell as the internal Vref 154. The Vref calibration controller 150 getsfeedback from the CML2CMOS 122 and determines the offset (e.g., offsetfor an internal DAC of the reference voltage calibration) that is usedto set or adjust the internal Vref 154 generated by the voltagegeneration circuit 110 (e.g., internal DAC). It should be noted thatduring step 1 (illustrated in FIG. 2), the second multiplexer 114selects the default Vref 113 received from the common node 115. Asdescribed below at step 2, the second multiplexer 114 selects aninternal Vref 154. By calibrating the offset and the low-swing Vref, thereceiver can be programmed to low-swing internal Vref mode. Thedual-mode calibration process continues as described below with respectto FIG. 3.

FIG. 3 is a block diagram illustrating the receiver architecture 100 ofFIG. 1 during the transition from a high-swing mode to a low-swing modeaccording to one embodiment. The single-ended transmitter toggles asingle command signal, a second calibration command, on the pin 108 toswitch the receiver to low-swing (e.g., high frequency mode) in step 304(step 3). The receiver decodes the second command (e.g., Vrefcalibration command), which initiates the CA Vref calibration of thereceiver for low-swing input-output (I/O). During step 3, the secondmultiplexer 114 selects the internal Vref 154 for the second commandsignal. The internal Vref 154 may be 125 mV reference, instead of 200 mVdefault Vref 113. In response to the second Vref calibration command,the receiver calibrates the internal Vref 154 to be per-pin dependent atsteps 306 and 308. At step 306 (step 4), a clock pattern or any of thedirect current balanced patterns (calibration pattern) can be receivedat pin 108 from the single-ended transmitter. The filter 116 cancalculate an average to get the common mode 111 using one of thefollowing options: 1) passive filters (e.g., RC filter); 2) switchedcapacitor filter; and 3) low bandwidth amplifier (e.g., voltagefollower). At step 308 (step 4), the preamp 120 receives the externalVref 151 on the pin 118 and the internal Vref 154 from the voltagegeneration circuit 110. The output of the preamp 120 is coupled to theCML2CMOS circuit 122 and the output of the CML2CMOS circuit 122 can befeedback to the Vref calibration controller 150. Using the external Vref151, the receiver architecture 100 can calibrate the internal Vref 154to a specified voltage (e.g., 125 mV). In one implementation during step308, the Vref calibration controller 150 includes logic that sets anoffset of an internal DAC of the voltage generation circuit 110 to setthe internal Vref 154. Alternatively, other voltage generation circuitsthan the internal DAC can be used to generate the internal Vref 154, ascontrolled by the logic of the Vref calibration controller 150. Anoffset value for the voltage-temperature (VT) drift in the internal Vref154 is compensated for during calibration by the Vref calibrationcontroller 150. The Vref calibration controller 150 applies the offsetvalue to the voltage generation circuit 110 (e.g., internal DAC) to setthe internal Vref 154.

It should be noted that an additional Vref calibration step could bedone for the toggled command signal (the second Vref calibration commandsignal). It should also be noted that the single-ended transmitter andreceiver of the CA bus boot up in a high-swing, low data rate mode, andtransition to a low-sing, high data rate mode. Other implementations canuse high-swing, high-data rate modes during startup, which can be usedto reduce or eliminate low speed startup. Described below with respectto FIGS. 15-18, in one embodiment, the receiver architecture cantransition a high-swing mode to a low-swing mode in four steps.

FIG. 4 is a high-level block diagram illustrating a single-endedcommunication system 400 that uses a transmitter 402 and a receiver 404with dual-mode swing support according to another embodiment. Asillustrated in FIG. 4, communication system 400 includes a transmitter402 (such as a memory controller), a receiver 404 (such as a memorydevice), and an interface 401 coupled between transmitter 402 andreceiver 404. The interface 401 includes a signal channel. Thetransmitter 402 can further include a signal-generating circuit 408,while receiver 404 can further include an amplifier/sampler 416, a Vrefcalibration controller 450 and a voltage generation circuit 410.

During data signal on communication system 400, signal-generatingcircuit 408 in transmitter 402 generates a signal 418, which is thentransmitted over the signal channel. Signal 418 is received by thereceiver 404 as received signal 418′. In particular implementations,signal 418 (and hence signal 418′) is a single-ended voltage signal,which is referenced to a ground level. For example, this ground levelcan be a ground node of a power supply, Vss. To recover the originalsignal 418 on receiver 404, signal 418′ is compared against a referencevoltage 420 generated by the voltage generation circuit 410, and thedifference between the two signals is sampled by amplifier/sampler 416.The voltage generation circuit 410 may be any of the voltage generationcircuits described herein. In some implementations, both signal 418′ andreference voltage 420 are referenced to a ground node of a power supply,Vss′. Ideally, amplifier/sampler 416 outputs signal 418″, which is acopy of signal 418. Of course, the actual signal 418″ may be affected bynoise. The receiver 404 may include other circuits to compensate for thenoise level. The receiver 404 further includes circuitries forinitializing and calibrating the amplifier/sampler 416, such as the Vrefcalibration controller 450. Moreover, although only a single signal 418is shown being transmitted from transmitter 402 to receiver 404, in manycases there may be multiple signals transmitted from transmitter 402 toreceiver 404, and communication system 400 may have multipleamplifiers/samplers for handing such multiple signals. Additionally, oneor more signals may be transmitted from receiver 404 to transmitter 402.Also, the transmitter 402 can send the signal 418 to more than onereceiver.

Transmitter 402 and receiver 404 may be located on the same integratedcircuit, or they can be located on different integrated circuits. Inother implementations, transmitter 402 and receiver 404 may be locatedon separate modules (e.g., separate cards) coupled by one or more buses.

Note that signal 418 may be a digital or analog signal, or any generalsignal capable of communicating information. In some implementations,signal 418 is a digital signal associated with memory operations. Inthese implementations, signal 418 can include read/write data, a controlsignal, an address signal and a clock signal. In specificimplementations, this digital signal is a binary signal comprising 1'sand 0's.

The Vref calibration controller 450 may be any of the Vref calibrationcontrollers as described herein. The Vref calibration controller 450receives an external Vref 451, such as on a pin 458. The Vrefcalibration controller 450 can control transitioning the receiver 404between the high-swing mode and the low-swing mode, as well as controlcalibration of the voltage generation circuit 410, which generates thereference voltage 420. The result of the Vref comparison 418″ (shown tohappen in the RX front end 117) is also fed back to the Vref calibrationcontroller 450.

In one implementation, the voltage generation circuits 410 includes aconstant resistor with variable current as illustrated in the voltagegeneration circuit 900 of FIG. 9. In other implementations, the voltagegeneration circuits 410 may include the other types of voltagegeneration circuits described with respect to FIGS. 10 and 11.

FIG. 5 is a high-level block diagram illustrating a single-ended memorysystem 500 including a memory controller 512 and a DRAM device 514 withdual-mode swing support according to another embodiment. The memorycontroller 512 includes transmitter 502 and the memory device 514includes receiver 504. In some implementations, memory device 514 is aDRAM device. However, memory device 514 can include other types ofmemory devices. The transmitter 502 and receiver 504 are similar to thetransmitter 402 and receiver 404 described with respect to FIG. 4. Thetransmitter 502 sends a signal 518 over the signal channel of theinterface 501, and the receiver 504 receives the signal as the receivedsignal 518′. The receiver 504 includes the amplifier/sampler 516, thevoltage generation circuit 510 and the Vref calibration controller 550that includes logic to set the Vref generated by the voltage generationcircuit 510. These components are similar to those described withrespect to FIG. 4. In particular, the Vref calibration controller 550may be any of the Vref calibration controllers as described herein. TheVref calibration controller 550 receives an external Vref 551, such ason a pin 558. The Vref calibration controller 550 can controltransitioning the receiver 504 between the high-swing mode and thelow-swing mode, as well as control calibration of the internal referencevoltage 520, generated by voltage generation circuit 510. The result ofthe Vref comparison 518″ (shown to happen in the RX front end 117) isalso fed back to the Vref calibration controller 550.

In one implementation, the voltage generation circuits 510 includes aconstant resistor with variable current as illustrated in the voltagegeneration circuit 900 of FIG. 9. In other implementations, the voltagegeneration circuits 510 may include the other types of voltagegeneration circuits described with respect to FIGS. 10 and 11.

In one implementation, the transmitter 502 is on a first integratedcircuit and the receiver 504 is on a second integrated circuit. Thefirst integrated circuit may include a host computer (e.g., CPU havingone or more processing cores, L1 caches, L2 caches, or the like), a hostcontroller or other types of processing devices. The second integratedcircuit may include a memory device coupled to the host device, andwhose primary functionality is dependent upon the host device, and cantherefore be considered as expanding the host device's capabilities,while not forming part of the host device's core architecture. Thememory device may be capable of communicating with the host device via aDQ bus and a CA bus. For example, the memory device may be a single chipor a multi-chip module including any combination of single chip deviceson a common integrated circuit substrate. The components of FIG. 5 canreside on “a common carrier substrate,” such as, for example, anintegrated circuit (“IC”) die substrate, a multi-chip module substrateor the like. Alternatively, the memory device may reside on one or moreprinted circuit boards, such as, for example, a mother board, a daughterboard or other type of circuit card. In other implementations, the mainmemory and processor can reside on the same or different carriersubstrates.

FIG. 6 is a flow diagram of a method 600 of operating a slave deviceincluding a receiver with dual-mode swing support according to anembodiment. The method 600 begins the slave device receiving commands ona CA bus from a master device while the CA bus is in a high-swing mode(block 602). The slave device initiates calibrations to operate the CAbus in a low-swing mode in response to the commands (block 604). Theslave device switches to operate the CA bus in the low-swing mode whilethe CA bus remains active (block 606). The slave device receivesadditional commands on the CA bus from the master device while the CAbus is in the low-swing mode (block 608).

In a further implementation, the method begins by booting up a DRAMdevice in a high-swing mode of operation. The DRAM device includes areceiver, a CA bus and a DQ bus. The DRAM device receives a firstcommand (e.g., low-swing transition command) from a memory controller onthe CA bus to transition the CA bus to a low-swing mode of operation,and the DRAM device transitions the CA bus to the low-swing mode inresponse to the first command. While in the low-swing mode, the DRAMdevice receives a second command (e.g., Vref calibration command) fromthe memory controller to initiate calibration of a Vref of the CA bus,and the DRAM device calibrates the Vref of the CA bus by the DRAMdevice. In a further implementation, the DRAM device operates the DQ busin the low-swing mode of operation.

As part of booting up, the DRAM device can operate the CA bus in adefault startup condition using a default Vref. The default Vref isgreater than the Vref for the low-swing mode. The default Vref may begenerated using a resister divider and a voltage supply (e.g., Vdd). Ina further embodiment, the DRAM decodes a first calibration command tocalibrate an initial offset and an initial Vref for the CA bus in thelow-swing mode and decodes a second calibration command to disablecommand decoding and to initiate calibrating the Vref. The Vrefcalibration can optionally be done on a per-pin basis for the CA bus.

In some implementations, the DRAM device can boot up in the high-swing,low-data rate mode on the CA bus. The DRAM device can then transitionthe CA bus to the low-swing, high-data rate mode.

In another implementation, a method begins by receiving commands on a CAbus at a slave device from a master device while the CA bus is in ahigh-swing mode, such as at startup of the slave device. The slavedevice and the master device each include dual-mode input-output (I/O)support to operate the CA bus in a low-swing mode and the high-swingmode. The commands received from the master device initiate calibrationof the slave device to operate the CA bus in the low-swing mode. Theslave device switches to operate the CA bus in the low-swing mode whilethe CA bus remains active and then receives additional commands on theCA bus at the slave device from the master device while the CA bus is inthe low-swing mode.

As described herein, the master device may be a memory controller andthe slave device a memory device, such as a DRAM device.

FIGS. 7-8 illustrate a flow diagram of a method of operating a DRAM anda memory controller according to another embodiment. Referring to FIG.7, the method 700 begins by the memory controller (CPHY) and the DRAM(MPHY) transmission levels use a high-swing Vref (e.g., 400 mV) at aboot frequency and an internal Vref (e.g., 200 mV), which is internallygenerated from Vdd (block 702). At block 704, the memory controller (MC)sends a mode register write (a first command) at the boot frequency toconfigure the DRAM device to CA Vref initial calibration mode (firstmode) and enables Vref calibration for the CA bus (e.g., CA[10:0]) andchip-select (CS) pins. In one embodiment, the boot rate may be between10 MHz to 55 MHz and the full rate may be between 166 MHz to 1600 MHzbased on various settings. Alternatively, other boot rates and fullrates may be used as would be appreciated by one of ordinary skill inthe art having the benefit of this disclosure. Also at block 704, theclock enable signal is set high (CKE=High), and the memory controllerwaits at the boot frequency for a specific amount of time (t_(RXOFFS))before sending a mode register command (e.g., mode register write (MRW)command) to switch the DRAM device to low-swing mode. It should be notedthat CKE pin behaves differently in CA Vref calibration mode (secondmode). At block 706, the DRAM performs receiver sampler offsetcalibration (Rx sampler offsetCAL) and Vref calibration. The Vrefcalibration may be done using various techniques as would be appreciatedby one of ordinary skill in the art having the benefit of thisdisclosure. Also, at block 706, the DRAM device switches to low-swingmode within the same amount of time referenced above, t_(RXOFFS). The125 mV Vref for the Vref can be generated from the external Vref pin,and CKE is still full swing, but correctly decoded as high as thecalibration does not affect this path. Also, at block 706, the DRAMdevice switches to the internal Vref mode with CKE being high. Blocks702-706 can be performed at the boot rate as depicted as blocks withdotted borders. In other implementations, one or more of the blocks706-706 can be performed at a full rate as illustrated in blocks 708-712of FIG. 7 and blocks 802-812 of FIG. 8. Blocks performed at the fullrate are depicted as blocks with solid borders.

At block 708, the memory controller changes the frequency to a fullrate. As described above, the full rate may be between 166 MHz to 1600MHz based on various settings. Also, at block 708, the memory controlleris configured for low-swing mode, and the CKE switches to low-swingmode, but is correctly decoded by the DRAM device as being high. Atblock 710, the memory controller de-asserts CKE and holds it low todisable command decoding, and the DRAM device detects the transition onCKE. At block 712, the DRAM device starts the CA Vref calibration on theCA bus (e.g., CA[10:0]) and CS pins after a certain pre-determinedamount of time (t_(VREFST)) when toggle patterns are received from thememory controller.

Referring to FIG. 8, the method 700 continues by the memory controllersending a half-rate toggle pattern on the CA bus (e.g., CA[10:0]) and onCSN (chip select not (or chip select bar)) continuously to the DRAMdevice within a specified time (e.g., within t_(CAENT), which is lessthan t_(VREFST)) (block 802). t_(CAENT) refers to a time interval thememory controller has to send pattern on CKE after t_(CAENT) (timeinterval) of issuing the MRW command that triggers the calibration. Thismay be maintained for the whole initialization period of Vrefcalibration. At block 804, the memory controller waits for theinitialization period to complete and asserts CKE to enable commanddecoding. At block 806, the memory controller sends a mode registerwrite to enable Vref calibration for CKE alone. Also, at block 806, CSNis low for the first cycle of the mode register command and high for therest of the time (CKE=high), and the DRAM device starts the CKE Vrefcalibration after t_(VREFST). At block 808, the memory controller sendsa half-rate toggle pattern on CKE continuously to the DRAM device withinthe specified time (e.g., t_(CAENT)) and CSN is held high and the CA bus(e.g., CA[10:0]) is set to don't care. This may be maintained for thewhole initialization period. At block 810, the memory controller sends amode register write to the DRAM device to disable CA Vref calibrationmode with CSN low during the first cycle of the command and CKE is heldhigh. At block 812, the memory controller begins normal traffic on theCA bus in the low-swing mode. It should also be noted that the internalVref of the receivers of the CA bus is optionally calibrated on aper-pin basis.

FIG. 12 is a diagram of a computer system 1200, including main memory1204 with dual-mode swing support according to one embodiment. Thecomputer system 1200 may be connected (e.g., networked) to othermachines in a LAN, an intranet, an extranet, or the Internet. Thecomputer system 1200 can be a host in a cloud, a cloud provider system,a cloud controller, a server, a client, or any other machine. Thecomputer system 1200 can operate in the capacity of a server or a clientmachine in a client-server network environment, or as a peer machine ina peer-to-peer (or distributed) network environment. The machine may bea personal computer (PC), a tablet PC, a console device or set-top box(STB), a Personal Digital Assistant (PDA), a cellular telephone, a webappliance, a server, a network router, switch or bridge, or any machinecapable of executing a set of instructions (sequential or otherwise)that specify actions to be taken by that machine. Further, while only asingle machine is illustrated, the term “machine” shall also be taken toinclude any collection of machines (e.g., computers) that individuallyor jointly execute a set (or multiple sets) of instructions to performany one or more of the methodologies discussed herein.

The computer system 1200 includes a processing device 1202, a mainmemory 1204 (e.g., read-only memory (ROM), flash memory, dynamic randomaccess memory (DRAM), a storage memory 1206 (e.g., flash memory, staticrandom access memory (SRAM), etc.), and a secondary memory 1218 (e.g., adata storage device in the form of a drive unit, which may include fixedor removable computer-readable storage medium), which communicate witheach other via a bus 1230. The main memory 1204 includes the receiverarchitectures 100, 400, 500 as described above with respect to FIGS.1-5, as described in more detail below.

Processing device 1202 represents one or more general-purpose processingdevices such as a microprocessor, central processing unit, or the like.More particularly, the processing device 1202 may be a complexinstruction set computing (CISC) microprocessor, reduced instruction setcomputing (RISC) microprocessor, very long instruction word (VLIW)microprocessor, processor implementing other instruction sets, orprocessors implementing a combination of instruction sets. Processingdevice 1202 may also be one or more special-purpose processing devicessuch as an application specific integrated circuit (ASIC), a fieldprogrammable gate array (FPGA), a digital signal processor (DSP),network processor, or the like. Processing device 1202 includes a memorycontroller 1212 as described above. The memory controller 1212 is adigital circuit that manages the flow of data going to and from the mainmemory 1204. The memory controller 1212 can be a separate integratedcircuit, but can also be implemented on the die of a microprocessor. Thememory controller 1212 may include the single-ended receiverarchitectures 1250 as described above with respect to FIGS. 1-5 asdescribed above. In addition, or in the alternative, the single-endedreceiver architectures 1250 may also reside in the memory device 1254.

The computer system 1200 may include a chipset 1208, which refers to agroup of integrated circuits, or chips, that are designed to work withthe processing device 1202 and controls communications between theprocessing device 1202 and external devices. For example, the chipset1208 may be a set of chips on a motherboard that links the processingdevice 1202 to very high-speed devices, such as main memory 1204 andgraphic controllers, as well as linking the processing device tolower-speed peripheral buses of peripherals 1210, such as USB, PCI orISA buses.

The computer system 1200 may further include a network interface device1222. The computer system 1200 also may include a video display unit(e.g., a liquid crystal display (LCD)) connected to the computer systemthrough a graphics port and graphics chipset, an alphanumeric inputdevice (e.g., a keyboard), a cursor control device (e.g., a mouse), anda signal generation device 1220 (e.g., a speaker).

FIG. 13 is a timing diagram of the receiver architecture with dual-modeswing support in a high-swing mode before transition to a low-swing modeaccording to one embodiment. The timing diagram of FIG. 13 includessignals for CK, CSN, CA<10:0>, CKE, and Vref (mV) at the DRAM device.The high-swing mode can operate at a boot rate before transition to thelow-swing mode.

FIG. 14 is a timing diagram of the receiver architecture with dual-modeswing support in a low-swing mode after transition from a high-swingmode according to one embodiment. The low-swing mode can operate at fullrate.

FIGS. 15-18 illustrate four steps of the transition from a high-swingmode to a low-swing mode according to one embodiment. FIG. 15 shows step1 in which the second multiplexer 114 selects the default Vref for highswing (e.g., 200 mV) and the first multiplexer 112 selects the signalreceived on pin 108. The output of the first multiplexer 112 and thesecond multiplexer 114 are coupled to the preamp 120, which feeds intothe CML2CMOS 122. The output of the CML2CMOS 122 is input into logic ofthe Vref calibration controller 150, which controls the voltagegeneration circuit 110. FIG. 16 shows step 2 in which the secondmultiplexer 114 selects the internal Vref generated by the voltagegeneration circuit 110, and the first multiplexer 112 selects the signalfrom the filter 116 to receive the calibration command. This can be doneto calibrate the internal Vref. FIG. 17 shows step 3 in which the firstmultiplexer 112 selects the signal received on pin 108. FIG. 18 showsstep 4 in which the first multiplexer 112 receives the signal fromfilter 116, and the second multiplexer 114 receives the internal Vrefgenerated by the voltage generation circuit 110.

In the above description, numerous details are set forth. It will beapparent, however, to one of ordinary skill in the art having thebenefit of this disclosure, that embodiments of the present inventionmay be practiced without these specific details. In some instances,well-known structures and devices are shown in block diagram form,rather than in detail, in order to avoid obscuring the description.

Some portions of the detailed description are presented in terms ofalgorithms and symbolic representations of operations on data bitswithin a computer memory. These algorithmic descriptions andrepresentations are the means used by those skilled in the dataprocessing arts to most effectively convey the substance of their workto others skilled in the art. An algorithm is here and generally,conceived to be a self-consistent sequence of steps leading to a desiredresult. The steps are those requiring physical manipulations of physicalquantities. Usually, though not necessarily, these quantities take theform of electrical or magnetic signals capable of being stored,transferred, combined, compared and otherwise manipulated. It has provenconvenient at times, principally for reasons of common usage, to referto these signals as bits, values, elements, symbols, characters, terms,numbers or the like.

It should be borne in mind, however, that all of these and similar termsare to be associated with the appropriate physical quantities and aremerely convenient labels applied to these quantities. Unlessspecifically stated otherwise as apparent from the above discussion, itis appreciated that throughout the description, discussions utilizingterms such as “encrypting,” “decrypting,” “storing,” “providing,”“deriving,” “obtaining,” “receiving,” “authenticating,” “deleting,”“executing,” “requesting,” “communicating,” or the like, refer to theactions and processes of a computing system, or similar electroniccomputing device, that manipulates and transforms data represented asphysical (e.g., electronic) quantities within the computing system'sregisters and memories into other data similarly represented as physicalquantities within the computing system memories or registers or othersuch information storage, transmission or display devices.

The words “example” or “exemplary” are used herein to mean serving as anexample, instance or illustration. Any aspect or design described hereinas “example’ or “exemplary” is not necessarily to be construed aspreferred or advantageous over other aspects or designs. Rather, use ofthe words “example” or “exemplary” is intended to present concepts in aconcrete fashion. As used in this application, the term “or” is intendedto mean an inclusive “or” rather than an exclusive “or.” That is, unlessspecified otherwise, or clear from context, “X includes A or B” isintended to mean any of the natural inclusive permutations. That is, ifX includes A; X includes B; or X includes both A and B, then “X includesA or B” is satisfied under any of the foregoing instances. In addition,the articles “a” and “an” as used in this application and the appendedclaims should generally be construed to mean “one or more” unlessspecified otherwise or clear from context to be directed to a singularform. Moreover, use of the term “an embodiment” or “one embodiment” or“an implementation” or “one implementation” throughout is not intendedto mean the same embodiment or implementation unless described as such.

Embodiments descried herein may also relate to an apparatus forperforming the operations herein. This apparatus may be speciallyconstructed for the required purposes, or it may comprise ageneral-purpose computer selectively activated or reconfigured by acomputer program stored in the computer. Such a computer program may bestored in a non-transitory computer-readable storage medium, such as,but not limited to, any type of disk including floppy disks, opticaldisks, CD-ROMs and magnetic-optical disks, read-only memories (ROMs),random access memories (RAMs), EPROMs, EEPROMs, magnetic or opticalcards, flash memory, or any type of media suitable for storingelectronic instructions. The term “computer-readable storage medium”should be taken to include a single medium or multiple media (e.g., acentralized or distributed database and/or associated caches andservers) that store the one or more sets of instructions. The term“computer-readable medium” shall also be taken to include any mediumthat is capable of storing, encoding or carrying a set of instructionsfor execution by the machine and that causes the machine to perform anyone or more of the methodologies of the present embodiments. The term“computer-readable storage medium” shall accordingly be taken toinclude, but not be limited to, solid-state memories, optical media,magnetic media, any medium that is capable of storing a set ofinstructions for execution by the machine and that causes the machine toperform any one or more of the methodologies of the present embodiments.

The algorithms and displays presented herein are not inherently relatedto any particular computer or other apparatus. Various general-purposesystems may be used with programs in accordance with the teachingsherein, or it may prove convenient to construct a more specializedapparatus to perform the required method steps. The required structurefor a variety of these systems will appear from the description below.In addition, the present embodiments are not described with reference toany particular programming language. It will be appreciated that avariety of programming languages may be used to implement the teachingsof the embodiments as described herein.

The above description sets forth numerous specific details such asexamples of specific systems, components, methods and so forth, in orderto provide a good understanding of several embodiments of the presentinvention. It will be apparent to one skilled in the art, however, thatat least some embodiments of the present invention may be practicedwithout these specific details. In other instances, well-knowncomponents or methods are not described in detail or are presented insimple block diagram format in order to avoid unnecessarily obscuringthe present invention. Thus, the specific details set forth above aremerely exemplary. Particular implementations may vary from theseexemplary details and still be contemplated to be within the scope ofthe present invention.

It is to be understood that the above description is intended to beillustrative and not restrictive. Many other embodiments will beapparent to those of skill in the art upon reading and understanding theabove description. The scope of the invention should, therefore, bedetermined with reference to the appended claims, along with the fullscope of equivalents to which such claims are entitled.

What is claimed is:
 1. An integrated circuit comprising: a plurality ofcommand and address (CA) pins to interface with a dynamic random accessmemory (DRAM) device having a command and address (CA) interface; and atransmitter circuit to transmit to the CA interface of the DRAM devicevia the plurality of CA pins: upon initialization, transmit command andaddress information using a first signaling frequency; transmit a moderegister write command to initiate calibration of a reference voltage ofa receiver circuit of the CA interface by the DRAM device; and transmita calibration pattern in connection with the mode register writecommand, the calibration pattern to be used by the DRAM device tocalibrate the reference voltage of the receiver circuit to sampleadditional command and address information at a second signalingfrequency that is higher than the first signaling frequency.
 2. Theintegrated circuit of claim 1, wherein the transmitter circuit comprisesa chip select interface to transmit a chip select signal to the DRAMdevice, the chip select signal to control command reception at the CAinterface, and wherein the calibration pattern is to be used tocalibrate a reference voltage of a receiver circuit of the DRAM deviceto sample chip select signals at the second signaling frequency.
 3. Theintegrated circuit of claim 1, wherein the transmitter circuit transmitsthe command and address information with a first voltage swing at thefirst signaling frequency.
 4. The integrated circuit of claim 3, whereinthe calibration pattern is to be used to calibrate the receiver circuitto operate with a second voltage swing that is smaller than the firstvoltage swing.
 5. The integrated circuit of claim 1, wherein thereference voltage is set to a default voltage level before thecalibration of the CA interface, and wherein the first signalingfrequency is a boot frequency.
 6. The integrated circuit of claim 1,wherein the transmitter circuit is configured to transmit the additionalcommand and address information at the second signaling frequency usingtermination that is coupled to a ground voltage potential.
 7. Theintegrated circuit of claim 1, wherein the transmitter circuit comprisesa clock enable (CKE) interface to transmit a CKE signal to the DRAMdevice, and wherein the CKE signal is to enable command decoding at theDRAM device, the calibration pattern is to be used to calibrate areference voltage of a receiver circuit of the DRAM device to sample theCKE signal at the second signaling frequency.
 8. The integrated circuitof claim 1, further comprising memory controller circuitry that controlsoperation of the DRAM device, wherein the transmitter circuit isconfigured as part of the memory controller circuitry, the integratedcircuit further comprising one or more processor cores coupled to thememory controller circuitry.
 9. An integrated circuit comprising: a chipselect interface to transmit a chip select signal to a dynamic randomaccess memory (DRAM) device having a first command and address (CA)interface, the chip select signal to control command reception at thefirst CA interface of the DRAM device; a second command and address (CA)interface to transmit, to the first CA interface of the DRAM device,using a first signaling frequency at initialization, command and addresssignals including a mode register write command to initiate calibrationof of a reference voltage of a receiver circuit of the first CAinterface by the DRAM device; and the second CA interface to transmit acalibration pattern in connection with the mode register write command,the calibration pattern to be used by the DRAM device to calibrate thereference voltage of the receiver circuit to sample additional commandand address signals and chip select signals at a second signalingfrequency that is higher than the first signaling frequency.
 10. Theintegrated circuit of claim 9, wherein the second CA interface transmitsthe command and address signals with a first voltage swing at the firstsignaling frequency.
 11. The integrated circuit of claim 10, wherein thecalibration pattern is to be used to calibrate the receiver circuit tooperate with a second voltage swing that is smaller than the firstvoltage swing.
 12. The integrated circuit of claim 9, wherein thereference voltage is set to a default voltage level before thecalibration of the first CA interface, and wherein the first signalingfrequency is a boot frequency.
 13. A method of operation of anintegrated circuit memory controller device that controls a dynamicrandom access memory (DRAM) device having a command and address (CA)interface, the method comprising: upon initialization, transmittingcommand and address (CA) information, to the CA interface of the DRAMdevice, using a first signaling frequency; transmitting a mode registerwrite command to the CA interface of the DRAM device to initiatecalibration of a reference voltage of a receiver circuit of the CAinterface by the DRAM device; and transmitting a calibration pattern inconnection with the mode register write command to the CA interface ofthe DRAM device, the calibration pattern to be used by the DRAM deviceto calibrate the reference voltage of the receiver circuit to sampleadditional CA information at a second signaling frequency that is higherthan the first signaling frequency.
 14. The method of claim 13, furthercomprising transmitting a chip select signal to the DRAM device, thechip select signal to control command reception at the CA interface ofthe DRAM device, wherein the calibration pattern is to be used tocalibrate a reference voltage of a receiver circuit of the DRAM deviceto sample the chip select signals at the second signaling frequency. 15.The method of claim 13, wherein transmitting the CA informationcomprises transmitting the CA information with a first voltage swing atthe first signaling frequency.
 16. The method of claim 15, wherein thecalibration pattern is to be used to calibrate the receiver circuit tooperate with a second voltage swing that is smaller than the firstvoltage swing.
 17. The method of claim 13, wherein the reference voltageis set to a default voltage level before the calibration of the CAinterface, and wherein the first signaling frequency is a bootfrequency.